Let the function f(t) in Example 17.1 be the voltage source v_{s}(t) in the circuit of Fig. 17.20. Find the response v_{o}(t) of the circuit.
From Example 17.1,
v_{s} (t) = \frac{1}{2} + \frac{2}{π} \sum\limits^{∞}_{k = 1}{\frac{1}{n} \sin nπt} , n = 2k – 1
where ω_{n} = n ω_{0} = n π rad / s . Using phasors, we obtain the response V_{0} in the circuit of Fig. 17.20 by voltage division:
V_{0} = \frac{jω_{n} L}{R + jω_{n} L} V_{s} = \frac{j2nπ}{5 + j2nπ} V_{s}
For the dc component (ω_{n} = 0 or n = 0 )
V_{s} = \frac{1}{2} ⇒ V_{o} = 0
This is expected, since the inductor is a short circuit to dc. For the nth harmonic,
V_{s} = \frac{2}{nπ} \underline{/ – 90°} (17.6.1)
and the corresponding response is
V_{o} = \frac{2nπ \underline{/ 90°} }{\sqrt{25 + 4n^{2} π² } \underline{/ \tan^{-1} 2nπ / 5}} (\frac{2}{nπ} \underline{/ – 90°}) (17.6.2)
= \frac{4\underline{/ – \tan^{-1} 2nπ / 5} }{\sqrt{25 + 4n^{2} π² }}
In the time domain,
v_{o} (t) = \sum\limits^{∞}_{k = 1}{\frac{4}{\sqrt{25 + 4n^{2} π² }}} \cos (nπt – \tan^{-1} \frac{2nπ}{5}) , n = 2k – 1
The first three terms ( k = 1 , 2 , 3 or n = 1 , 3 , 5) of the odd harmonics in the summation give us
v_{o}(t) = 0.4981 \cos (πt – 51.49°) + 0.2051 \cos (3πt – 75.14°)
+ 0.1257 \cos (5πt – 80.96°) + . . . V
Figure 17.21 shows the amplitude spectrum for output voltage v_{o}(t) , while that of the input voltage v_{s}(t) is in Fig. 17.4(a). Notice that the two spectra are close. Why? We observe that the circuit in Fig. 17.20 is a highpass filter with the corner frequency ω_{c} = R/L = 2.5 rad/s , which is less than the fundamental frequency ω_{0} = π rad/s . The dc component is not passed and the first harmonic is slightly attenuated, but higher harmonics are passed. In fact, from Eqs. (17.6.1) and (17.6.2), V_{o} is identical to V_{s} for large n, which is characteristic of a highpass filter.